We are doing already frequency response of amplifiers. Today we start with the first of the most important device of analog which is an operation amplifier nicknamed, short named opamp. We want to talk about, of course I will show you little later. This is a figure which I am showing you which is a sketch for two stage opamp. There is a possibility of Thursday in real opamps which is right now put dotted one, okay. The first stage is essentially what we call high gain stage which is followed by another gain stage which is basically high swing stage and then it is connected to buffers which is typically push pull types, output amplifiers as they are called and that gives the output to you. Next opamps used are single ended. What does that mean? The output is only at one output. There are no differential two outputs, okay. But let us say if you wish to have two outputs there are possibilities and I will show you one circuit which does that. So a CMOS opamp which is either double ended or single ended. Normally if it is double ended you use current source biasing and if you are using single ended opamp normally it is current mirrored biasing, okay. Normally it is not necessary you can do any kinds of biasing but normally it is done through current mirrors. This normal word should be taken seriously because not every circuit uses exactly the way I say individual requirements may push you to some other ones, okay. So this is typically what we want to know. So what is the first stage, second stage and third stage which allows you to do this kind of features, high gain followed by high swings and then finally the buffer out. Buffers are always required for driving larger loads, okay. And in the case of MOS circuits 99.99 they will be capacity loads. So you are driving a large capacitor which may be the input capacitance of the next chip or next stage of the circuit, okay. And like in the case of digital circuit we typically expect the load at least 4 times these yawks which is called FO4 loads. So even in this case at least whatever the highest capacitance you put 10 times CL so that becomes the maximum possible load. But in general in our design right now we will specify for what load this needs to be designed. The features of OPAN will discuss when we start designing OPAN what exactly the parameters we are worried about like gain CMAR, bandwidth and what else. But let us do some basic thinking on this. So once I declare that I want a high gain stage the possibility of such high gain stage is either through a cascode amplifier but it will give only generally single ended outputs and require large power dissipations. So we will go for DIFAM. So the first stage of OPAN is normally a differential amplifier or difference, okay there is a word I keep saying differential amplifier and a difference amplifier I will differentiate later. But in looks sometimes they are same, sometimes they are not. The difference amplifier is essentially outputs are also different. Two outputs, two inputs which are required in many filter organizations, okay. So first stage is a DIFAM which whose output can be single ended or can be double ended and it is given to another stage which is normally high swing high gain stage. Most of the gain picked up here the rest gain is picked up here plus swings are improved. Then there is a last stage which I am showing you buffer, output buffer or this output amplifier. Typically it is pushful kind but not necessarily everywhere but take it normally it will be a pushful. What does pushful means? Are you have the top transistor will be on or the lower transistor will be on, okay like a normal output stage of any digital hardware. So that is the but the importance there is they can drive larger capacitance because they can provide larger currents, okay. Yes. Sir, arc line is a high swing. Yeah, it is a gain stage but it gives the output swings. V out max V out min is picked up from there, okay and not from the DIFAM stage, okay. Is that clear? Then in most op-amps for the case of stability or by without doing thinking over it there will be a feedback capacitance connected. CGDs for example always there or other parasitic capacitance may appear which may give you output to input connections at the at least the output stage, this stage and in that case you will have a feedback. Now this feedback also creates feed forward, okay. So in all our analysis we try to avoid feed forward situations, okay. What does feed forward can give you? A 0. So we are trying to see that 0 does not appear at least in the range of frequencies where we wish to operate. Now the feedback is what we few days, few minutes we will discuss later but if you see carefully this, if you look at the DIFAM, the first two transistors may be here is may I put it, new slide just for the heck of it. Just look at either of them. This M1, M2 receives input voltage and converts them into GMV1, GMV2 kind of currents. So this is essentially called V2I converters. When these I's are fed to these they give an output which means current to voltage converter starts here. Is that clear? This block is V2I converter, this block is I2V converter, okay. So this first two stages, DIFAM has two parts, one is the V2I converter part, the other is why I am giving you these figures but this is how one designs, which area we are looking into, okay. So the first part is converter from V2I, they are the I2V which together makes DIFAM followed by a gain stage like shown here or shown here. Now this gain stage you can see from here since this is an output, M5 is receiving VGS and therefore converts currents. So next stage of this is a V2I converter and that current passes through M6. So this will then give you I2V converter at this output, okay. So typical OPAM, two stage OPAM has two V2I and two I2V converters, okay. Is that point clear? This is only a statement, nothing very big just to tell you how fundamentally one should look the circuit from inside. Is that okay? So first is V2I then I2V then V2I and then I2V, this is a two stage OPAM. The two possible, of course they are minimal but these are the two most popular ones which are used in OPAM designs. This is a double ended output and this is a single ended output. So in this, this is your DIFAM. Now since it is not diode connected, so normally current is not mirrored, actually you apply through VB another transistor and create ISS and you also bias this VBB these to make it current sources, okay. So as just W by L of the last transistor to suit this currents which is going to go down. Is that not the other way? The VB and W by L of this is so adjusted that the currents which I am receiving from the current source are essentially received at the ISS which you want to use as a design spec, okay. So since this is from where VB I can create voltage reference preferably if you want a very nice stable reference, band gap reference or at least VT references. You can see it is a double ended so one output is taken here, one output is taken here and then you have two single stage output stages which is essentially the same one which is in the single end also. So I can create a VO1 and VO2 and if I choose M5, M6 not identical I will have VO2 separate from VO1, is that clear? So I have a double ended output of my choice which is proportional to input voltage VIN, is that clear? Please remember I can make a ratio of this, I can make a ratio of this and can change the currents in this and therefore VO1 and VO2 that is V2I and I2V converter can be modified to suit different VO1 and different VO2 for the same input VIN. This is essentially double ended output if all are equal then the VO1 will be equal to VO2 then you do not need that. If you are using same then why do you want to? At times you still need to, in a layout it is sometimes preferred to have same output going other two sides so you may as well use this but that does not help too much because it consumes power for nothing. So this is a, as I said not very often used but if needed can be employed in many opiants they are specific opiants which gives you double ended outputs. Many of the LM series which is a low noise opiants they are double ended outputs. Even 8576 is also double ended very famous low power low noise device. This is the one which is most of the 741 series 741, 747, 725, 723 whatever standard opiants you see in the labs they uses single ended outputs, a diffam whose load is decided by diode connection. We have already done analysis for this. We have also done this individually so it is not that they are too different it is only a question of load which you put there. In these cases most times both this M6, M7 if there are any other stage are driven through a current mirror the biasing is not shown here. So there will be a biasing circuit which will give you a current mirror and that same output is connected to a mini transistors as you want to have same currents is that correct? Okay so when I start looking into this design all that I have to design is the W BIOS of this and W BIOS of this to meet specification. What else I can design the size of M7 which may design the RSS or RSS values okay. Because I can mirror whatever current I want is that clear? I do not have M7, M6 same either I can have different M6, M7 if need rises normally I will not do that but if I need I can do that because I just have to make different W BIOS for this. The problem there is different how much will be decided by this because this is going to push the current. So it is not too much in your hand okay. Is that okay? Okay so my end product is OTAN will be given some specification to me and all that I will design or I will get an output is sizes of all transistors okay that is what design is about because once I know the size they are not done layout may be in between before we go details one class on the design layout may be helpful just a minute I will come back to it. A typical transistor I already said this is a black line which is think it is red or pink it is a gate this is a green line which is diffusion this is source drain gate this is essentially what you are doing this is the transistor cross section those drain and if you have window here let us say oxide on the top and contact here so I can open a contact here these are all oxides contact here this may be my drain this may be my great and this may be my source so I can open a window inside this and make a metal contact on this I can open a window here and I can put a metal contact here I can open a window here cut and I have a contact here this is called layout what is the transistor length and width here from the this is length and this something is width so what do you show here which is your length and which is your width obviously the poly thickness is your length and poly width on this diffusion width are essentially a width of transistor so this is essentially convert this is what I designed from circuit and once I design I give you designs they transfer it on the silicon to create this actual structures so my gate at the end for any designer is to create patterns that is what all that we are going to do at the end so what do I need lengths and weights if you give me this I will be able to draw the correct sizes of transistors and if that is so I believe that the technology people can translate what I said on silicon and therefore the performance should actually be as values of W well I have chosen if it does and I will took something and come back once again that is called turn around so this please remember so as a designer we are our output is only sizes okay some specification electrical special given using all that circuit analysis we should arrive at sizes and of course connections because to transistor how will we connect them how many points will go on a single load so this is another connectivity problem which is interconnects so all that we design is the W by L for transistors and possible interconnects interconnections of thickness and widths because that will decide R and C for the circuit so these are all that we design as from a designers point of view technology people pick up this mask actually print one by one and typical process is around 24 mask for a standard CMOS if you want extra anything else you thought I should do another this another mask it may go as high as 32 mask in some cases each mass cost hell hell of a means millions and dollars so do not just say I could put another window and do something because that may cost the profit to expenses is ratio which people calculate in D1 they may do that extra also because D runs should be sold in millions same way they may say do it in my purpose because they are off shell any number are sold okay but if you say some specific chip they will be sold hundreds or a company only will buy that much or 1000 2000 then you cannot put extra money okay so vendor will decide what we will do so exactly as a designer my job is only to get sizes okay interconnects I believe I can independently handle those not really easy that is becoming the worst part right now but for the sake of NLM right now I say okay I am interested right now in W buyers of the oil transistor which I see and if I put their values I can create this and if I create this I believe that technology people will be able to translate into a actual silicon chip that is the output from us transferred to actual circuits is that clear so please remember for us it does not matter any other thing is not relevant for us of course you may have limitation of bandwidth you may have limitation of gain powers lee rates we are max we are mean ICMR you may put any PSIR CMIR you may put any number of constraints or specs for you but at the end of this what best among them you can get for the design you are asking find W buyers for all of them so I will give a opamp design later for those who have access to SMDP sites otherwise ask someone who works in VLSL lab there is already an opamp design sitting on my SMDP site under one course which I did from IEP is called there is an opamp design for a butter I will actually change my specs for your course so that it is not be identical but the method will remain same so those who wish to see that can even now see that okay it is around 10-12 pages of 15 slides or more more just to show you how designs go at the end okay is that pointless of what is our is having taken a circuit and given specification okay this is also our choice this one this one any other architecture you can choose either depend on your thinking but then this it should meet the given specs for given technology node as well because you will be specified 0.25 micron process 0.35 0.18 or 96 whichever technology they say that must conform to that technology node what will change there beta beta dash will change vts will change power supply will change so many parameters and their variations will change and therefore the design will become even tougher as I go down in the node values okay so designing 0.35 is the ideal or 5 micron will be the best because everything will work so when we design why we choose 5 micron but then we are sure that in case per say you translate I assure you 100% it will work okay but if someone does it on 45 nanometers me and you will keep kissing may or may not okay that is the problem with technologies okay so having shown you is to hardware part this one which I am going to use now okay and there are two stages the defam stage in a output stage second gain stage so the net gain is everyone into AV2 AV1 is nothing but the gain of a defam AV2 is gain of a single ended up what is this just a minute before you write which is this amplifier is please remember I never said all input should be only on N channels this is a P channel device which is taking an input you can see an input is coming there this is the load for it so this is a common source amplifier with a P channel driver okay so do not look the other way that the input is given to 5 which is a P channel device okay and to keep it minus Vgs this actually the source is given higher voltage okay so that minus values are automatically created is that clear that we do in CMOS that is what we did here okay so please take it this is a standard defam followed by a gain stage single common source amplifier what is W by us will give you whatever currents it will keep will give you GM sign ROS and once I know them I can I will be able to evaluate gain of this stage and gain of this stage okay so the example is the AV1 will be minus GM1 R02 by R04 for the defam the AV2 will be minus GM5 into R05 R06 so the gain finally two stage gain is GM1 GM5 R02 R05 R06 please take it in the first case the output is picked up here is that clear these two transistors are not diode connected so they have ROS okay so they may be GM parallel one by GM parallel but R0 will take care of them whereas in this case one upon GM is its R0 actually R0 parallel one upon GM but I am not taking output here anyway is that clear so that base terms are missing simply because I am not picking output from that in I am only picking output from here so GM times either this GM or this GM because currents will be half off into R parallel of these two is the output is that correct same way whatever I am receiving here this size ratio R06 in parallel R05 into GM of R05 GM of 5 is the gain for common source this is that clear so it is very simple what we did and therefore not gain and again solving we already saw defam we already saw common source common drain common everything so we just substitute whenever is that okay so there is nothing very big this is a defam this is a common source amplifier there I have written it but you can see that I can just multiply the two gains I also know I can calculate GM 1 and GM 2 by writing 2 beta 1 ideas 1 2 beta 2 ideas 2 beta 1 normally a 99.999 will be equal except the variation part the thresholds will be equal the sizes will be equal but do not think 3 and 4 will have same W1 as 1 and 2 because they are loads they may be different values compared to this why other other reason also they will be different sizes the lower transistor what kind and kind the upper ones are P kind so even for the same current new ratio will appear okay so for that matter their sizes may be equal between M3 and M4 but will not be same as M1 and M2 as we did earlier okay so I can calculate GM 1 GM 2 RO 1 RO 2 RO 3 RO 4 all this knowing the currents and once I know the current now the question is how much current this will draw I am example I show you this please remember this current there it is showing from here I do not know what is the size of M6 I need okay I will see that this current is same as this current okay we have both P channels same current flows here to flow the same current here this will not be same current here is that clear to you let us say this is ISS this is ISS by 2 this is ISS by 2 so current which will flow through M6 is not ISS but ISS by 2 so for that W by L will be different is that point clear though it is made here but their size may not be equal is that clear to you so this are the issues we should quickly look at it from where current I that is why the first figures are shown P2I I to be P2I this is P2I which is pushing current in the load is that clear so the current is coming from M5 and not from M6 is that clear to you yes you can see from it why it should have because if these two values are very different which you can I mean there is no physical problems the problem with this the current which it will draw and current which it will able to push may not be sufficient then if it is too high from there at best this current can be pushed here okay now if that increases too much then this will not be able to sustain this maximum current is that correct let us say the ISS goes through so that till ISS it will happen but beyond that I can always increase 4 times 8 times 20 times then the currents cannot be overall be actually available to you so device will not remain in this device may go out of saturation therefore the best possible solution is run this current into this which you both transistor to remain in saturation is that clear these are the tricks when you do simulation if you do hopefully some you realize what have you change yourself and figure out what has happened okay and that is the trick yes it will I please take it this is this gate and this is the source this value is can always be equal to this if the currents are same if this current and this current are same this values will be always equal so that is why I am saying I am sizing that way I am exactly telling you this I is equal to beta by 2 W by L VGS minus I am keeping things fixed so that I can push the same current is that clear is essentially not this is divided by these this is the ratio this is an AC current you are you do not confuse between ACs and DCs is that clear the first part was the DC biasing situation now I am talking of AC current please get this 2 moves differently working okay so I did expressions I figured out I can just tell you we are just running the jokes what we have done I can find R o 1 by 1 upon lambda 1 R is by 2 R o 2 R o 3 similar way I can calculate all R o's and I can calculate all GM's okay and if I know one of them then I can start like all lambda are equal let us say for P channel and all lambda are equal for N channels so only 2 hours will be required to be calculated for those ISS is known so go back and calculate GM for them and keep doing till you get W bias for all example I am just going to show this is the formula is only that I designed use for design of a defam is that correct defam to this so I have an example for you you know this doesn't look to be very nice expressions is that okay what I did I am just trying to say I can evaluate R o I can evaluate GM in terms of size and currents ISS by 2 and W by else will decide my hours and GM's is that clear if alpha lambdas are known typical lambdas for 5 micron process is 0.06 per volt okay others may have 0.04 0.025 but which one is better higher or lower 0 is the ideal that is always infinite okay 0 is the ideal but 0 you will not get the larger technologies are larger lambdas okay in general so it typical values which my problems taken from boys book is 0.06 is typical value they choose but in your life when I give a problem I may not choose 0.06 it may be much different from the then I may use a technology of 0.25 so the specs given by 0.25 I will use it in your calculation right now as I said I am using boys data and therefore I am using his values but otherwise please take it the given data is coming from where technology file on a spice there is a technology file which will give you all specification for that technology node of a transistors is that clear so pick up actual data from there which in my case I will give a table or at least give the values okay so is that point clear so let me start having a problem which may clarify many of those doubts let us say at total bias current in defam is 20 micro amps I says I was one upon lambda ID and GM is under root 2 beta ideas it now it juggled it low I agree it is relevant but that much you can think okay yeah look over here it must have put a job here I was single ended all single ended you know as I said double ended are specific devices required not that they are not used by the user differential systems but as of now okay please remember I am using just to give ideas using data from boys Baker these work or these work so pardon me if that data is copied as it is and problems is maybe slightly modified or used there also but I have solved myself I have not checked with them if the bias current is chained on as 20 micro amps then the each arm will get a DC will be of Isis by 2 which is 10 micro amps so I can calculate if given betas lambdas okay so I calculate GM 1 which is 2 beta 1 Isis by 2 I know beta n dash I just do not know right now W by L but that is what I need to know R01 is equal to R02 lambdas are given to you which is lambda by 2 Isis by 2 R02 parallel is 1 upon lambda 2 plus lambda 4 there will be equal but if you wish you can write lambda 2 plus lambda of into Isis by 2 is that I am not saying lambda equal then I have lambda 2 plus lambda 4 times Isis by 2 is 1 upon R02 parallel R04 so this value I calculate 0.06 it is 0.06 per volt both of them all actually I am not chosen same actually even that is not true P channel lambdas are different from N channel lambdas for that is what I say for the simplicity okay so what is the current in each arm of a defam Isis by 2 is beta 1 by VGS minus VT 1 so root Isis root beta 1 by 2 is VGS minus VT 1 I am using this for what purpose you know the expression become any do I know this for a 5 micron process I know VGS 1 how much it will be V over V plus VT for this technology V over is 0.37 volt as I declared earlier okay voice book is that okay what is the purpose of doing this if I know these two values okay then and if I know this value then I know beta dash then what can I calculate W by L that is the purpose of all this evaluation is that here root Isis is beta 1 by 2 so if I do this so if we have is chosen 0.37 volt for a VT of 0.83 for N channel and 0.9 minus 0.9 for P channels then VGS 1 is equal to VGS 2 equal to 0.83 plus 0.37 which is for a 5 fold supply VSS is 2.5 minus VD is 2.5 total supply voltage is 5 fold for which these values are valid so I get VGS 1 equal to 1.2 Isis is 20 micron each is a half current and if you solve this that becomes W by L N is equal to 15 by 5 and by same argument same current going up I can I will have to calculate VGS 3 and VGS 4 from where instead of 0.83 use 0.9 okay because I still believe excess voltage is same for both N channel and P channels so if I know VGS 1, VGS 2, VGS 3, VGS 4 I will be valid W by L of 1, 2 and for N channel as well as for 3 and 4 for the P channels. Please I have already said whenever I calculate W by L's I neglect all 1 by lambda VDS terms okay but when I calculate arrow I actually use it because other arrow becomes infinite okay so all calculations of W by L's and GM's you may forget about 1 plus lambda VDS term okay but whenever you will calculate arrow that time do not neglect lambda because that will create high walks for you okay. So I know these values now to find an open loop gain what is the open loop gain the first stage GM 1, arrow 2 parallel arrow 1 is the first stage GM 6, arrow 6, 5 and 6 is not providing that name 5 and 6, arrow 5 parallel arrow 6 is the GM 6 5 times that is the gain for the second stage so this is GM 1, GM 5, this is arrow 2, arrow 5, arrow 5, arrow substitute the values already I have evaluated is that correct so if you substitute this I did not calculate but roughly I did some calculations this is called back up envelope mine calculation so no envelope but just by looking at it yeah, yeah, yeah, yeah. So around just write down this typical value which will get is around 2500 what should the unit both per voltage amplifier specified properly they does not matter because the ratio but even then do specify which amplifier you are using so give a unit V by V now why this whole game was is that point clear I am able to evaluate and why this L was written no feedbacks are right now used in any part therefore it is called open loop gains the next part that we will put close loops now that is the next thing we want to do so right now itself I started writing open loop okay so that later we do not have to say what is open loop so I have calculated is that everyone written so AAL is typically I am not exactly it may be 25, 24, 90 or 26, 50 whatever it is because my hand calculation has just cut out but along that now the game which we want to see very clearly from this expressions of AAL GM may root ISS or lambda may ISSA denominator so when lambda times RO sorry GM times RO so proportionately 1 upon ISS has to be 2 stage key square arrival so we say open loop stage gain for a 2 stage amplifier open is essentially inversely proportional to ISS is that correct this is a feature which you should use for your designs is that clear what is the feature I got why did all this calculation I figured out if I reduce the current by 10 okay what I will achieve low power fantastic 2 things I may lose image I may improve bandwidth also okay I may lose bandwidth also but I may get gain higher another thing I may hurt is that I will see the slew rate it will not charge faster okay so that if I want very high slew rate I want higher bandwidth I will increase GM that is I increase ISS but I will lose the gain because gain and bandwidth will go opposite is that clear to you so this is what design has to which one you have to cater to okay and how much closer you can come from either side so I wrote again hence the increase of ISS may improve bandwidth but decrease AOL or vice versa please remember in real life we are not just worried about these values but we want that these values remain constant okay for what variations process variation temperature variations and even power supply variations so if any variation in power supply appears currents will change any variation in W Biles of process kilometers change currents will change and in any time temperature changes so are the current change so our worry is we do not want gain to vary with any such environmental or design related variations this where that they should be very low sensitivity for them essentially makes system should have some mechanism which actually monitors the change and corresponding proportional something it returns to input which corrects it either way if it is increasing it should decrease if it is decreasing it should increase such a system which we do is called feedback systems is that clear so why feedback because these are not constant values in other assumption right now we assume everything 5 volt remain same W Biles are same everything is same between M1 M2 itself they will not be same okay and if there is plus 5 percent minus 5 percent you are 10 percent variation which is possible this may not be possible this may not happen on your layouts because that is a screen graphic does very well but when it goes to silicon the lithography technique does not allow everything as good okay okay so we wish to visit before we go to the open design that since I want a stable gain stable everything I like to quickly look into little bit of feedback which I did in second year many of you might have done it many of you still remember better than what I know many of you never wanted to know so long now either way so let us refresh ourselves from the feedback because we know feedback and stability that related obviously this word is true that one kind of feedback may actually spoil the stability the other may actually stabilize so all other tricks is to see that the one which stabilizes always remains and in some other case that is the joke every designer in a lot says if I am designing an amplifier it oscillates if I am designing a oscillated amplifiers so okay so the trick is the amplifier must work as an amplifier and the oscillator must oscillate at a frequency okay and the issues are always the opposite okay when you design a oscillator you want something happen and suddenly damping starts so what happened same way amplifier you think everything should be okay then it starts giving outputs like this so the values are very important in design and these should be understood from the basic perspective of feedbacks okay so let us look at feedback once again typical feedback system is shown here as I say this is only a precursor to what we are actually looking for but I am just going quickly through the basic feedback theory which will make us understand why we are doing something so this is an open loop amplifier this is the signal r i f is the input impedance seen from that this is some kind of a summer or adder signal term okay the impedance seen by the open loop amplifier is r i and this is an input x i output resistance seen inside out to the open loop amplifier is r o output is x 0 and the impedance seen outside x 0 is r o f which receives essentially some network impedance from beta the feedback is through a fraction of x 0 is returned please remember beta is always less than 1 so fraction is returned to the summer and then x s plus x f will happen depending on the sign either x s minus x f occurs or x s plus x f occurs depending on the sign of 2 which you receive okay so a l is called open loop gain beta is called feedback factor normally beta is passive element okay normally but need not be okay and if it is need not if it is the other way then the analysis becomes very very complicated okay but right now we will say assume constant so we say x 0 is the gain times x i x i is the input to open loop gain amplifier x 0 is the output so x 0 is a l j j omega x i a l j omega x i is nothing but x s minus x f the way right now signs are shown x i is therefore x s minus x f because of this I wrote this and x f is nothing but beta times x 0 so x 0 is a l x s minus a l beta x 0 so if I am going to find the closed loop gain which is x 0 by x s then it is a l upon 1 plus a l beta the sign of this can become minus depending on the a l is of what sign is that clear a l is negative it will become 1 minus a beta if it is 2 stage it may become 1 plus a beta so right now I did not want to put a sign in real life I will put a minus or plus as it appears okay now this fact that closed loop gain is related to open loop gain through a l upon 1 plus a l beta and in the control system theory or in feedback theory we give some names for this if you have any book these are standard definitions in any book including the book yesterday I said about said Rasmith and me so they may be here a l is the open loop gain this is called mixing area this is called sampling area so you sample the output return to input to a mixing so a l is gain without feedback acl is the closed loop gain with feedback and we define a term a l beta as the loop gain okay as the loop gain also it is called return ratio some books like grace day on Mayer's book use it return ratio okay so if you are policy Raj who happens to see the Gray and Mayer's book will a loop gain name will a return ratio Bode also use the return ratio not the loop gain okay so essentially the 1 plus a beta actually decides the feedback available to you okay because a l is the open loop gain and this is additional term which is coming so it is deciding the part coming from feedback okay these are definitions if you see the expressions everyone has these are standard and as I said at least the fourth year students who are taken my course second this slide I actually copied from that you can see this number appearing here is that okay one upon a beta decide how much you are away from you if open loop is a l that is the term which is changing the gain by putting 1 plus a beta so if that is larger a l will be net gain is smaller if it is smaller that is higher but it will never reach a l anyway okay unless beta is removed if let us say the loop gain a beta is greater than 1 then a l a l cancels or a cancels and we see closed loop gain is 1 upon beta is this good or bad it is very good because beta is a passive network okay which is relatively can be kept constant okay so if you have a feedback and you are gain for a l loop gains are higher then you are safer because your feedback is very much stable okay so why are you in all this calculation is we always assume beta gain once you do this it is constant no actually beta itself may vary okay beta register high obi temperature coefficient like you are okay but that is how we say R1 upon R1 plus R2 hold on hold on the company them okay however beta is less than 1 then ACL can be greater than 1 and however ACL is a 0 1 plus a beta can change with beta and value and sign of a 0 okay so there are 2 possible ways the feedback can affect us if you see our figure if the x sign x f are in the same sense then they add and their opposite sorry are the opposite sense they add if they are in the same sense they actually subtract okay battery high plus minus plus add ho jaiga plus minus minus plus subtract ho jaiga so essentially one which reduces the XI value from its excess value we say it is negative feedback but it does not mean always reduce it it also can correspondingly change output will return less feedback and try to adjust okay where do you think positive feedbacks are used oscillators for all amplifier will prefer negative feedback and that is what my issue was that when I design an amplifier I will end up in this when I design an oscillator I will end up here okay because both our functions have some parameters one may dominate over other and you forgot to bring them well so okay so basic idea is to design a negative feedback circuit just for the heck of completeness if you are a negative feedback what essentially we gain in an amplifier is that okay everyone this is standard okay the first thing it actually does is desensitivity of the gain what does desensitivity means it reduces the sensitive if you see a closed loop gain which is a 0 upon 1 plus a 0 l you can write I have sometimes I wrote a 0 sometime a well so it is a 0 upon 1 plus a 0 beta d acl is d a 0 1 upon differentiate here then we say d acl is d a 0 upon 1 plus a beta this still connecting this d a 0 this into 1 plus a 0 is come multiplied here okay so this essentially give me d a 0 by a 0 is equal to 1 upon a 0 beta d acl by acl so you can see any change in a 0 will be reduced by 1 plus a beta for the closed loop system so you are desensitized change in a 0 is now reduced in the acl system by as much as 1 upon 1 plus a beta so this is called desensitivity parameter or factor so any percentage change in a 0 please remember this is the standard technique of showing sensitivities as if d a 0 by is d y by y equal to d x by x correlation though percentage in this percentage change in how much okay so essentially they say the change percentage here will be reduced this because by this factor so this is a desensitivity the second advantage which feedback gives from an amplifier specific is let us look at the so the second feature of nearly feedback is it improves the bandwidth okay let us say your open loop gain is a mid band upon 1 plus s omega 0 where omega 0 is the first pole dominant pole we call it done a m upon 1 plus s omega 0 is a 0 a l is a 0 right now then with the negative feedback acls is a ls upon 1 plus a ls beta substitute this quantity here and here okay so you get a m upon 1 is mid band gain a m upon 1 plus s by omega 0 upon 1 plus a m upon s plus 1 into beta collect the terms and define acl 0 as a m upon 1 plus a m beta which is independent of frequency so dc closed loop gain dc closed loop gain a m is the dc mid band gain for open loop system so I get acls is acl 0 upon 1 plus s time s by 1 plus a m beta times omega 0 so now the pole has been shifted from omega 0 to 1 plus a beta times omega 0 so you have improved your bandwidth by this much amount by just putting a feedback is that clear so why is that clear but if you see closed loop gain what it has done it has reduced by that much amount so bandwidth is increased by that much amount okay please take it these are my notations names you may have if you are reading from any other book and they are followed but follow universally what you follow once like spice uses K as the beta okay but some spice new versions use K by 2 or rather beta by 2 as K but think of it this can vary you because you are losing 50% on that okay like spice level 3 level 49 versions use the beta dash by 2 as K dash whereas the 3.3 of the old versions in G spice they only use beta dash as K dash the next of course this I made a statement obviously the bandwidth improves gain falls a third most important reason why one works with the feedback near a feedback says it actually reduces what we call nonlinear distortions in amplifiers what does nonlinear distortion means if you have a characteristics V0 versus V in for a given V in value if the linearity is not held then the since the curve is not linear it is a nonlinear term so when you actually find V0 in terms of V in your square cube polynomial terms will appear so much of the power or energy will be lost in other frequencies okay second harmonic third harmonic and higher harmonics whereas you want all the energy should go to fundamental so that means larger the slope change more and more energy is being lost that is V0 is not getting at that frequent for null frequency exactly transferring from V in okay that is called harmonic distortion the third harmonic distortion is the worst among all because that phases in exactly with the first ones so it gives huge interference so in RF design or any other designs the various THD but that will see later so let us say this is the kind of characteristics without feedback and in this range V0 V in is linear beyond this of course it changes the slope it may actually fall further so these are nonlinear terms so any input here or here with this slope will give you second and third or fourth harmonics however if you add a feedback you are just now seen gain is something like reduced now but but this but now you can see this frequency term up to which sorry sorry that is what I was saying how it is opposite okay that is fine so what essentially is time to say is as I change dv0 by dv in changes that means the linearities correspondingly changing so the idea behind putting a feedback is increase linearities okay so what is the purpose then you may increase linearity but your gains will be correspondingly different from your requirements so if the bandwidth will be different but at least for large signal operations probably you will be able to operate better okay okay so this is the three things why everyone goes for linearity feedbacks so from where the in other opiants or anywhere from where or any amplifier where the feedback is coming in a transistor normal transistor if common source for example is there where if the which is the feedback which is coming from Cgd okay Cgd is the output node she is the input node so the capacitance between gate and drain essentially is always available to you as a feedback factor okay so irrespective whether you put any external C there Cgd is always going to put you in negative feedback system okay and if that happens that is why systems have lower bandwidth we have calculated with Cgd but it is relatively will be stable operations one more stability that she will build actually increase but doing that what else will you see that that is our designs okay so we want to use this before we quit for the day here is something which you should know there are the two terms we use in feedbacks or any bode system of frequency response we call those terms as gain margin and phase margins okay these are most important parameters in design we will be specified phase margin for an amplifier okay or if not specified as a designer you will have to choose it how much I should have should I have 45 degree phase margin 50 degree phase margin 55 degree phase margin or 65 or 90 okay you may choose either of the phase margins how will they influence the performance is what we are going to see okay so what is the phase margin we will like to see this is our case loop system the case loop gain is as upon 1 minus as beta s and as I said we define the loop loop gain as as beta s here the s is taken minus so sign is going accordingly there is a standard criteria which is called Barkhausen criteria for oscillations or non instability which says a j omega 0 into beta j omega 0 which is l j omega 0 should be less than the magnitude y should be less than 1 for stability where omega 0 is the frequency at which the loop gain phase is 0 I repeat omega 0 is the frequency at which the loop gain is sorry the angle of phase of that is 0 angle means phase phase is 0 at that frequency at that frequency a times beta must be less than 1 then the system will remain stable in case of oscillator what we will do it we will actually break this to make it oscillate okay because gain is minus though this is taken as like this but this sign is taken as a return with a minus signs because the gain is less than db the way we calculate okay so you will just check it we will come back to it again now here is the important graph which is given in every book if not you can note down from here this is a representative graph nothing very this is the bode plot I am plotting a loop gain versus frequency okay let us say I have a pole P1 where the loop gain starts falling from this frequency P1 and let us also say for design the second pole is at the gain bandwidth point which I can design tbw is this where the gain becomes 1 the pole actually occurs there okay is that point clear the P2 pole occurs right here this is just to explain nothing it may occur later or it may occur earlier but just to make the case important study case is that the first pole is here second pole is actually starting here at this point okay we know from the Bode's plot that once the poles this 3 db point goes the loop gain will start falling by minus 20 db per decade okay and it reaches if there is no pole till then it will go to the 0 db point or it crosses the omega axis at this point which is your gain bandwidth point and let us say the second pole occurs here that will also give you another 20 db per decade fall so this 20 let the second pole 20 so the next fall will start going by 40 db if there is another pole somewhere here then a 60 db it will start falling down afterwards let us say the third poles occur here at this point 60 db will start falling but once the gain falls below minus 20 db or even 0 db it is not a gain anyway is that correct gain means log of something which is positive only if it is positive db otherwise it is a fraction and if it is a fraction you may still call it a gain but it is not really a gain so gain is only up to this as long as it is plus db it is okay now if you if you have done your complex algebra well and as last day I did tell this tan inverse or the angle for this is tan inverse imaginary by real essentially gives me what they call argument or tan inverse points and for these you study it if not some other day at first pole it should at least have 45 degree down from the mid band point mid band point start 180 degree because that is where the loop gain starts okay so from 180 at the pole it should have gone to 45 degree down because this slope is 45 degree per decade why 45 tan inverse 1 is 45 so there is a 45 degree so from 180 it goes to 135 at the pole position 45 degree down per decade assuming okay at the pole and it continues to fall by 45 degree per decade as the frequency increases but since there is no pole ahead then below this after this total of J1 J is over 90 degree the phase will become constant and it continues to remain constant but it wants that at the second pole it should go 45 degree further down so from this 90 degree it should go to 45 degree so this 45 degree per decade must cross at 45 degree point at the second pole is that clear so this therefore slope becomes something like this and this is the point please remember these are the points of interest to me at the pole P2 or at this gain bandwidth point the phase of loop phase loop gain phase is how much 45 degree is that clear if you increase further this gain 60 dB or 40 dB down then finally phase will become 0 okay phase will become 0 if you further go down it will actually increase further minus of that value as if you say when the oscillation starts when the output and input becomes in phase if they are out of phase they will remain in negative feedback stable situation what we are trying to see now is if when the gain is 0 you are still in the negative feedback phase 45 degree you are away from it is that correct let us say at this point would have occurred here I do not have figure here somewhere then what would have happened the gain would have been positive a 0 and your phase now is 0 other side which means the signal is now returning phase with the input is that correct which is the condition of growth that is instability. So to keep it stable what is the criteria when the gain is loop gain is positive the phase should not cross 0 so the margin up to this is available to you is called phase margin so how much is phase margin with me here 45 degrees so 45 degree is the phase margin available till that time the gain you can see from here beyond this the gain has already crossed 0 and my phase has not gone to 0 is that correct beyond if this could have gone somewhere here the gain would have remained positive and phase would have crossed 0 then I would have in phase component in the feedback in which case the growth would have started so this is essentially called phase margin then at 0 degree phase if the gain is negative then you are safer this is called gain margin at 0 degree phase how much you are away from GBW point is it called gain margin okay right now this is negative but let us say if you are the opposite side gain margin will be positive and phase margin will become negative which means you will have an unstable situations is that correct so in normal case gain margins are not specified because they essentially represent 5 in a way so we only say as long as phase margin is 45 degree why 45 degree is important for me why not even as long as it is anything between 45 and still safe what is the worry we do not want to go below 45 anything any additional capacitor parasitic appears how much phase it can give you 90 degree okay that may push it down earlier than what you thought okay so the minimum because 50 percent point I have to get it so I say at least 45 I should have so that the worst is gain margin is 0 at phase margin is 0 so you are exactly cutting each point is that clear so the minimum phase margin for stability is 45 now we will see tomorrow some more details of this and improve that the phase margins are essentially adjusted because what will phase margin will do they are deciding poles is that correct we know poles decide the bandwidths okay so by changing the phase margin you are also designing the bandwidths for the amplifier so how much about the 90 also you say very safe very safe may have a lower bandwidth because then only this can occur okay that very safe may create your bandwidth very very small so you need higher bandwidths and you also need safe margins so somewhere between 45 is very lower so never tried 55 degree to 65 70 degree is the ring in which and this number has something to do with transient response also which we will see next time zeta functions we are right now looking which frequency response frequency response if I see a time response I will suddenly see something else is happening at the phase changes okay and that I will say okay how much margin I have really to work with see you next time.


What's up guys, today we have the end of an era. You might have noticed in yesterday's video that the back wall looks a little different. I mean we're missing some stuff, there's stuff kind of like behind me on the ground whereas I still can't point the right way. Yeah, I'm still pointing the wrong way but we'll figure it out. There's stuff on the ground, the wall's not, it looks different. Why is that? We have officially moved on from a very important part of the channel and that important thing is my old apartment.  So things have changed quite a bit and I've moved out of the apartment. I am now in a new house, Chelsea and I bought, not new, we bought a house, it's not new. It wasn't built in 2023 or 24 now I guess. So we've moved out and I actually have way more space but as you guys know if you've ever moved before it takes a very, very long time so I've been trying to get set up and everything but it's taken a while but it's a very exciting update. We're moving out of the apartment which it's a little sad because that's where we pulled the red eyes black dragon out of the LOB box, the blue eyes shining dragon. All those really cool poles were in that apartment but the more exciting thing is I now can move around in my own space because before it was a tiny room I'll probably show a video of what it looked like before I left in this video or maybe in another, actually I might say that for another video we do a little tour or something at some point which we're not going to do in this video because I'm not editing this video at all. I watched the one from last year, I literally did not edit it so I'm doing that again because I mean why edit this kind of thing. So we'll show that in a future video. Well, if you want to see it, so if you want to see it, let me know in the comments. Do you want to see maybe a tour and maybe like a little flashback to what my room looked like before I left which a lot of you guys asked for. I never did because I couldn't move. There was nowhere to go. There's stuff everywhere so I'll show you. I have a couple rooms now that I'm using which is pretty exciting. So a little sad that that's coming to an end but very excited about the future with the new house. So I'm also going to bundle that announcement in because I want to make an announcement so you guys know, hey, I'm moving, I'm out. I'm in a new spot with a little channel update for 2024. So back in 2023, I did a channel update at the beginning of the year and I want to check in with how we did. So one of the big things that was not channel related but I let you guys know is a personal thing. I wasn't going to drink soda in 2023 and a lot of you guys who have been to the streams have asked, hey, how's the how's the no soda going? And I've answered that but if you have not been there to see those answers. I actually did not drink soda all year. So I actually achieved that goal. I think at one point I accidentally drank a carbonated beverage because I didn't know. I took one drink of it and then I was like, that tastes like carbonation. So I didn't drink it. So technically I did drink but the carbonated beverage or whatever. But I also, you know, that's the intention that matters. You know, I didn't drink at the rest of the time. So I think I did really well doing that. Another one was my schedule. I was going to try to wake up at a different time. I'm getting a call from Chelsea right now. Sorry, Chelsea. If she calls again, it's serious. So we got to answer but what was I saying? Yes. So I was going to wake up at a different time, try to get my schedule more normal because if you wake up super late, then it gets, you know, like my previous schedule was wake up at noon and then everyone's been awake for seven hours, you know. And it just, your schedules don't align very well and then you're awake at 4 a.m. and stuff like that. So I was trying not to do that. I wasn't completely successful with this one. I did pretty well at the beginning of the year and most of the way throughout the year at waking up at a normal time to kind of align my schedule with normal working hours and people at the post office open and stuff like that. But there were days where I definitely did not make that happen. So this was not as successful as the soda. I'm going to try to implement this again in 2024 to at least have that pressure on me to do it. So that one, those are the check-ins for that. I don't think I really talked about my like YouTube subscriber goals. I had those. We didn't hit those, by the way. We'll talk about how we did this year. But we're going to talk about how the channel did and the channel back in 2022. We had 28.1 million views this year. We actually had 20 or 31.9. So we actually went up in terms of views, which is pretty awesome, especially since, you know, the market for you give the interest in you give us down a little bit. So having that go up is pretty cool. But you have to consider that the year before we didn't have shorts all year and short. Well, we did. I just wasn't posting this year. I had shorts all year. So a lot of those are shorts views, which don't really count as much in terms of like monetary value in terms of, you know, gaining subscribers and stuff like that. But it was pretty awesome to see that the shorts were doing well and stuff like that. And speaking of that, we had a four and a half million view short, which was a record for me. I've never had a four and a half million view video. The most we'd had on a regular video was like two million on the top 10 best trading card polls. So this one was like went crazy. So it was really cool. And we only gained. I say only last year we had 68.5 K subs gained this year. We only gained 44 and a half, which at this point, I mean, I've reached 220. What are we? Whatever rat right now, which is a very high number for Yu-Gi-Oh. And I'm super happy with that. I'm very happy with you guys watch the channel and stuff. So it's kind of coming to a slow down, you know, which I think is pretty normal, but obviously I'm excited about growing. So hopefully we can, we can bump that back up next year. We'll have to see. I mean, I'm doing my best, but you can't really control how YouTube goes. You just kind of have to go with the flow. Cause sometimes it'll be a bad week. She's got to keep posting. That's why I post every day for the last over a thousand days. So that's just a little update for you guys. Pretty cool to see the 32 million basically. That was a pretty cool view count. And hopefully that'll continue. So throughout last year we had the 25th anniversary stuff the year before we did a, the every pack opening for 150 K, which was pretty awesome. This year we didn't do anything like that crazy for the specials, but we did have the 25th anniversary stuff all year. I was trying to keep up with all those different like releases and stuff. I think it was a pretty awesome year. Some of the stuff I liked more than others. You can see my top 10 video. I'm not editing the video. So who knows if I'll remember to put this here, but I did the top 10 sets of 2023. Go check that out. If you missed it, there were some I really liked some I didn't. I think Konami did pretty well on some and not so well on others, but that's just how it goes. And we also did guess that price season one for, I think it actually started technically in 2021, but a lot of the episodes were this year. The series actually had over 800,000 views, which was pretty amazing. I was not expecting the series to really get that popular. The moist critical episode was the biggest. I mean, surprise, surprise moist critical is big. He's very big YouTuber. 200,000 views on that one. So it was about a quarter of the views, but there was a lot of other people that even if the views didn't do that well, we got some really cool creators on there. And we've started up. If you have not seen, guess that price season two. We've changed up the format a little bit to a way that I think is actually more fun than the previous one. And we're going to have some returning guests, some new guests, some people that you guys have requested. Already in the first episode, I've already messaged and aligned with. So get excited about that. If you like, guess that price. I really like doing it. It's a nice change up from doing an opening because we do openings basically every day. So doing something different and you go related as well. It's kind of hard for me because I don't do like gaming, cut, like the actual. Dueling content very often, which I think would be pretty cool to maybe do some live duels or something like that now that I have more room. We'll have to see if we do that in the future. But. Overall, guess that price was super successful. And I think season two is going to be really more fun. So I'm excited for you guys to see it. Go check out Simo's episode already. Me and Simo did the first episode. It's pretty cool. So I don't do want to talk about one more video that we uploaded this year and just reflect on it. The Yu-Gi-Oh has a big problem video was actually, I think my most impactful video in terms of the Yu-Gi-Oh community because every time I would go to a event after that, people would say, Oh, I really loved your video about the big problem or whatever. And then I even see people regurgitating when I said back to me, like sometimes I'll say, you know, I'll put up a short or something and has a price on there and then somebody will comment, Yeah, but Konami is destroying this stuff or whatever. And I'm like, you know, I made that video, right? So that happens sometimes. And it's pretty cool to see like if I have noticed a problem and others have noticed a problem and I made a video about it, that people actually see it and relate and think, Oh, yeah, that's, that's probably true. I think that we probably need to get this fixed. So who knows if it'll get to Konami's ears. I'm, I would guess they saw the video, maybe not the everybody at Konami. I'm sure somebody at Konami saw it because based on the feedback I was getting like in person, not just like on in the comments, people saying, I really like that video. That was a great video, you know, it brought to light some really important stuff.  I'm not going to reiterate what was in the video, but you guys saw it. So that was pretty cool to see that kind of impact. We have over 50,000 views, which is less than some of the other views or some of the other videos on the channel, but I feel like more people watched it and like, you know, remembered it versus like some of our, like every pack opening is super exciting. Not everybody necessarily remembers every second of that video because they are very long. But if, you know, if you want to go watch it, go check those out. We have two of them. So very cool. So I wanted to talk about that. Now we'll do a little update on like Twitch this year. I, oh, another goal. I forgot to bring this up. Last year I did, I said I was going to do Twitch three days a week and I did not do it every week, but up until about, I think it was November when I got sick right before the one on stream. I had basically done it every week. I think there was one where I was gone. I did like two days, but November I missed like a week and a half because I couldn't even talk. So reasonable. And then December I missed some because of the move. So I haven't been streaming the last like week or week and a half, something like that on Twitch right now. But we've been pretty consistent on there. I'm pretty proud of myself for doing that, especially since I've basically been doing Pokemon content and the few dedicated viewers are there, but not many of you guys watch the Twitch stream. So I'm proud of myself for sticking to it even though it's not necessarily like a monetary thing that we're making money back from. The good side of the Twitch streams, besides just hanging out with the, you know, big fans of the channel, which I really appreciate you guys. Goldy, unholy fat man. Let's try to think of some other ones. Europa, thank you guys for being at a lot of the streams. There's some more people that I'm that I'm not mentioning. I know they're going to be sad because there's only like 20 of them. So all you guys are there all the time. I really appreciate you guys for coming out to the Twitch streams. We both mostly do Pokemon for the Poker Rocks channel. And the Poker Rocks channel has actually done really well this year. It gained like three or 4,000 subscribers is up to 5,300. We had two huge videos that did super well. I think it would be doing even better. I just don't have that much time to actually put into making videos because those videos take really long because you got to do an entire run, can nits it down. I have an editor that's working with me. He's doing a great job, but he can only work as fast as I can get him the stuff, which sometimes it can take a while. So I'm really happy with how Poker Rocks is doing. I think it's going to continue to do well if we keep putting out quality content like we have. If you have not yet checked it out and you like Pokemon challenge content, not Pokemon trading cards, a lot of people are like, when are you going to post an opening? I won't be posting openings on Poker Rocks. I'll probably post a Pokemon opening here before Poker Rocks because here is trading cards and it makes more sense. So if you haven't checked that out and you like Pokemon challenge stuff, go check it out because we're going to be doing more stuff. I'm working on another video right now. We're currently on the farthest run into Pokemon Radical Red I've ever done. So I'm super excited because that game is super hard. I'm on the easy mode. I know I'm not on the hardcore mode. It's too hard for me. Okay guys, I might get there one day. And finally, I think Ruxen Live. We did, we're doing Ruxen Live a lot last year, the year before 2023, 2022. But I just didn't post a lot there this year because we basically pivoted to all Pokemon content on Twitch. Not always, but basically. So there wasn't anything to put there. I am eventually going to put out a chicken sandwich to your list video that I did with my brother like six months ago. But who knows when that'll happen. There's just too many other things to upload. So that's just another thing. Ruxen Live, it's dead right now. Might come back in the future. So don't unsubscribe. Who knows? It might come back. It won't be, you know, you don't need to unsubscribe because I'm not posting. So it's not going to be annoying. So maybe it'll come back at some point. I think we've gone on long enough with the channel update. You guys know we've moved in now. Super exciting. You saw a video yesterday with this background. So I'm wondering, we haven't posted that video yet. I'm wondering how many of you guys are going to be like, what's going on with this background? And this is the answer. So thank you guys so much for the support in 2023 and previously all the way back to when we started the channel. Basically 2019 when we started doing the UGOTCG content. So I appreciate all you guys. Thank you so much for the support. We're going to continue to basically do what we've been doing getting dressed that price back and hopefully adding some other cool wrinkles now that I have more space. And that is really it for this video. If you have questions for me, make sure to put them in the comments. I want to know, you know, if you have an idea for something you think I should do in the future. I might not do it, but I might also do it. So I might read it and think that's a good idea or maybe that's an idea that I could spin off and change to something that I would really want to do. So let me know your ideas in the comments. Thank you guys for watching and supporting the channel in any way that you do it, whether it be a Patreon, shout out to all my Patreon slash YouTube members, whether it be watching, whether it be subscribing, whether it be people just donating to streams such as Ian. Thank you Ian for all your donations this year on the big and last year for all the big videos. So thank you guys so much. I will see you guys in the next video. Peace.


Welcome back to the weekly ranking show. My name's Cam Williams and with Wimbledon done and dusted We have some changes of the rankings, but not in the way that we used to seeing of course There was no points awarded to the Wimbledon winners So we've got players that have dropped down the rankings even though they've won but let's start with the results of last week So we had Wimbledon two events obviously one of the women one of the men's let's start with the past results Starting with the ladies Wimbledon final we had Rabakina taking out de beurre in the final three six six two six two to lift her first trophy Of course two first-time finalists and it was a very fun final and over on the men's side We had Novak Djokovic defeating Nick Kirios in the final in four sets four six six three six four seven six To lift another Wimbledon trophy his fourth in a row and his 21st grand slam But as I said players weren't rewarded in the rankings. They were only penalized Let's have a look at the women's rankings for this week Let's talk about the WTA rankings first We had Igor Shriantek staying at number one despite her only making the third round But wasn't penalized that badly still way ahead in the rankings But on Shri Beurre who made the final of Wimbledon has dropped three spots because she's lost a lot of points from her quarter Final last year and didn't get any points this year because of what happened with the Russians not playing and everything else So she got penalized she goes down number five Contivate goes up one spots a number two with Zachary going up two spots number three and Bedoss is staying right in the middle there at number four not moving So some changes to the top five despite the results going to the player that got penalized So it's very weird to see the rankings like that Sabalinka stays at number six dropping a lot of points from last year's semi-final But not enough to lose her spot and another player who lost all their ranking points was Plishkova She dropped down eight spots out of the top ten completely last year's finalist allowing Collins to go up to number seven Pagula to go up to number eight Mugaruta to number nine and Emirata Kanu is officially a top ten player She goes up to number ten in the rankings due to Pushkova dropping out completely So again players that didn't get rewarded for this year's tournament, especially Rabakano I mean she didn't get any points for this tournament unfortunately and of course Jaburre she dropped down big time It's been crazy with the rankings for this week Let's have a look at the race of the finals and there's no change because of course no points were awarded So Yggish Vwontek still the only player to qualify at this stage with Jaburre coming in second Gov comes in third Pagula in fourth Sakari fifth Kazakina in sixth, but Ossir in seventh We have Benchich at number eight Kudamatova at number nine and Daniel Collins rounds out the top ten No one getting any points this week So everybody stays the same as they were last week having a look at players that have gone up in the rankings Which has been very hard to find but players that got rewarded I guess because other players fell down Coco Goff. She's at a career high ranking number eleven in the world Mainly due to Pleskova falling out of the top ten So she's got I guess a bonus despite not getting any points for Wimbledon and Anissa Moeva who had a good Wimbledon She did get a boost in the rankings again due to players dropping down ahead of her She goes up to number 22 in the world three spots higher than last week players that have dropped down the rankings outside the top Ten Kerber last year semi-finalist She goes down 12 spots number 31 in the world and Tom Manevich Despite doing exactly the same thing that she did last year make the quarter finals of Wimbledon She dropped 27 spots to number 71 in the world So again a huge mess on the rankings this week due to the points not being rewarded to the players that earned them having a look At the ATP rankings this week, and it's just as weird as the women's Mehvedev he stays at number one was very of coming in at number two But no back Jokovic the winner of Wimbledon drops four spots I mean can you believe that he drops four spots down at number seven making way for Players below him to go up one spot with Rafa going into number three since he pass goes up to number four Root up to number five and Alcarez goes up to number six Jokovic fitting in at number seven the Wimbledon champion dropping four spots It's actually it's it's crazy to be able to say that I don't think we'll ever be able to say that again unless they strip the points at another tournament in the future But it's a weird situation Roobler comes in at number eight alias seam at number nine and Yannick Sinner He's gone up three spots into the top ten again due to players dropping down the rankings who lost points and didn't get points For this year so Yannick Sinner gets rewarded. He's back in the top ten having a look at the race to the finals now And again players haven't been rewarded points, so it stays the same Rafa Nadal He's at number one He is very close to qualifying for the ATP finals and had Wimbledon been worth points He probably would have qualified he's at number one City pass comes in at number two with Alcarez at number three root at number four Zverev comes in at number five Mehvedev comes in at six with those alias seam at seven Roobler at eight Fritz at nine and Novak Djokovic He slots in at number ten he would have been at number three or four had the points been rewarded So very unlucky there for Djokovic He still might qualify despite Wimbledon being worth nothing having a look at the players that have gone up in the rankings again Very hard to find but some players that played well away from Wimbledon So we have Nakashima who played well out Wimbledon He goes up seven spots because players dropping down ahead of him He goes into the top 50 for the first time career high Ranking at number 49. So he kind of got rewarded in a weird way for his fourth round and Montero He goes up 16 spots to a career high 73 because he won a challenger event during the second week of Wimbledon So he got rewarded based on a challenger result and goes up a lot of rankings because all the points dropping ahead of him From Wimbledon those players fell down while he got some points from that challenger having a look at the players that have Dropped down in the rankings and it's two players that played well at Wimbledon last year Baratini he drops down four spots in number 15 last year's finalist had Wimbledon been worth points He still would have dropped down because remember he had COVID before the event had to withdraw and Shava Varlov He drops down seven spots number 23 in the world because of last year's semi-final points dropping down But again, he didn't have a great tournament either So maybe these guys would have dropped down anyways because they didn't get to play or they had poor results And couldn't save those points that they had from last year. So there you have it What a weird day for the rankings great day for Wimbledon It was great fun at a great two weeks, but the rankings are an absolute mess without those points now We are hearing that maybe they'll award the the ATP and WTA finals race They might give the points out for those two tournaments to events But we haven't heard anything officially yet, but on the world rankings No back jokovic winning Wimbledon dropping in the rankings on stripper getting to the final dropping in the rankings So weird, let me know in the comments below. What is the weirdest part of this ranking system? Are you happy with it? I mean surely no one's happy with it By the way, Roger Federer is completely out of the rankings altogether. You can't find him in the rankings He has no points. So he's gonna have to start from scratch when he comes back But again, let me know down in the comments below. What do you find about?